Double data rate (ddr) memory controller apparatus and method

ABSTRACT

A computer-implemented method includes an act of configuring hardware to cause at least a part of the hardware to operate as a double data rate (DDR) memory controller, and to produce a capture clock to time a read data path, where a timing of the capture clock is based on a first clock signal of a first clock, delay the first clock signal to produce a delayed first clock signal, adjust the delay such that at least one clock edge of the delayed first clock signal is placed nearer to at least one clock edge of at least one data strobe (DQS), or at least one signal dependent on a DQS timing, and produce a modified timing of the capture clock based on the delay of the first clock signal.

COPYRIGHT NOTICE

A portion of the disclosure of this patent document contains materialwhich is subject to copyright protection. The copyright owner has noobjection to the facsimile reproduction by anyone of the patent documentor the patent disclosure, as it appears in the Patent and TrademarkOffice patent file or records, but otherwise reserves all copyrightrights whatsoever.

PRIORITY CLAIM

This application claims priority as a Continuation of U.S. patentapplication Ser. No. 16/909,871 filed on Jun. 23, 2020, currentlypending, the contents of which are incorporated by reference.

U.S. patent application Ser. No. 16/909,871 claimed priority as aContinuation of U.S. patent application Ser. No. 16/584,600 filed onSep. 26, 2019, registered as U.S. Pat. No. 10,734,061 on Aug. 4, 2020,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 16/584,600 claimed priority as aContinuation of U.S. patent application Ser. No. 16/296,025 filed onMar. 7, 2019, registered as U.S. Pat. No. 10,586,585 on Mar. 10, 2020,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 16/296,025 claimed priority as aContinuation of U.S. patent application Ser. No. 16/049,693 filed onJul. 30, 2018, registered as U.S. Pat. No. 10,269,408 on Apr. 23, 2019,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 16/049,693 claimed priority as aContinuation of U.S. patent application Ser. No. 15/996,365, filed onJun. 1, 2018, registered as U.S. Pat. No. 10,242,730 on Mar. 26, 2019,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 15/996,365 claimed priority as aContinuation of U.S. patent application Ser. No. 15/926,902, filed onMar. 20, 2018 registered as U.S. Pat. No. 10,032,502 on Jul. 24, 2018,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 15/926,902 claimed priority as aContinuation of U.S. patent application Ser. No. 15/722,209, filed onOct. 2, 2017, registered as U.S. Pat. No. 10,229,729 on Mar. 12, 2019,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 15/722,209 claimed priority as aContinuation of U.S. patent application Ser. No. 15/249,188, filed onAug. 26, 2016, registered as U.S. Pat. No. 9,805,784 on Oct. 31, 2017,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 15/249,188 claimed priority as aContinuation of U.S. patent application Ser. No. 14/882,226, filed onOct. 13, 2015, registered as U.S. Pat. No. 9,431,091 on Aug. 30, 2016,the contents of which are incorporated by reference.

U.S. patent application Ser. No. 14/882,226, in turn claimed priority asa NonProvisional Patent Application of U.S. Provisional PatentApplication Ser. No. 62/063,136, filed on Oct. 13, 2014, currentlyexpired, commonly assigned with the present application and incorporatedherein by reference.

U.S. patent application Ser. No. 14/882,226 also claimed priority as aContinuation-In-Part of U.S. Utility patent application Ser. No.14/752,903, filed on Jun. 27, 2015, registered as U.S. Pat. No.9,552,853 on Jan. 24, 2017, which in turn claims priority as aContinuation of U.S. Utility patent application Ser. No. 14/152,902,filed on Jan. 10, 2014, registered as U.S. Pat. No. 9,081,516 on Jul.14, 2015, which in turn claimed priority as a Continuation of U.S.Utility patent application Ser. No. 14/023,630, filed on Sep. 11, 2013,registered as U.S. Pat. No. 8,843,778 on Sep. 23, 2014, which in turnclaimed priority as a Continuation of U.S. Utility patent applicationSer. No. 13/172,740, filed Jun. 29, 2011, registered as U.S. Pat. No.8,661,285 on Feb. 25, 2014, which in turn claimed priority as aContinuation-In-Part of U.S. Utility patent application Ser. No.12/157,081, filed on Jun. 6, 2008, registered as U.S. Pat. No. 7,975,164on Jul. 5, 2011, all commonly assigned with the present application andincorporated herein by reference.

FIELD OF THE INVENTION

This invention relates to circuits that interface with memories, inparticular DDR or “double data rate” dynamic memories. Such circuits arefound in a wide variety of integrated circuit devices includingprocessors, ASICs, and ASSPs used in a wide variety of applications, aswell as devices whose primary purpose is interfacing between memoriesand other devices.

BACKGROUND

Double Data Rate, or “DDR” memories are extremely popular due to theirperformance and density, however they present challenges to designers.In order to reduce the amount of real estate on the memory chips, muchof the burden of controlling the devices has been offloaded to circuitsknown as DDR memory controllers. These controller circuits may reside onProcessor, ASSP, or ASIC semiconductor devices, or alternately mayreside on semiconductor devices dedicated solely to the purpose ofcontrolling DDR memories. Given the high clock rates and fast edgespeeds utilized in today's systems, timing considerations becomechallenging and it is often the case that timing skews vary greatly fromone system implementation to another, especially for systems with largeramounts of memory and a greater overall width of the memory bus.

In general, the industry has responded by moving towards memorycontrollers that attempt to calibrate themselves during a power-oninitialization sequence in order to adapt to a given systemimplementation. Such an approach has been supported by the DDR3 standardwhere a special register called a “Multi-Purpose Register” is includedon the DDR3 memories in order for test data to be written prior to thecalibration test performed during power-on initialization. The circuitryon memory controllers typically used for receiving data from DDRmemories normally incorporates features into the Phy portion (Physicalinterface) of the memory controller circuit where the controller canadapt to system timing irregularities, this adaptation sometimes beingcalibrated during a power-on initialization test sequence.

FIG. 1 Shows a typical prior art DDR memory controller where anAsynchronous FIFO 101 is utilized to move data from the clocking domainof the Phy 102 to the Core clock domain 103. Incoming read data dq0 isclocked into input registers 105 and 106, each of these input registersbeing clocked on the opposite phase of a delayed version of the dqsclock 107, this delay having been performed by delay element 108.

Asynchronous FIFO 101 typically consists of at least eight stages offlip-flops requiring at least 16 flip-flops in total per dq data bit.Notice also that an additional circuit 109 for delay and gating of dqshas been added prior to driving the Write Clock input of FIFO 101. Thisis due to the potential that exists for glitches on dqs. Both data andcontrol signals on a typical DDR memory bus are actually bidirectional.As such, dqs may float at times during the transition between writes andreads, and as such be susceptible to glitches during those time periods.For this reason, typical prior art in DDR controller designs utilizingasynchronous FIFOs add gating element 109 to reduce the propensity forerrors due to glitches on dqs. After passing through the entireasynchronous FIFO 101, read data is transferred to the core domainaccording to Core_Clk 110. Additional circuitry is typically added toFIFO 101 in order to deal with timing issues relative to potentialmetastable conditions given the unpredictable relationship betweenCore_Clk and dqs.

FIG. 2 shows another prior art circuit for implementing a DDR memorycontroller, in particular a style utilized by the FPGA manufacturerAltera Corp. Portions of two byte lanes are shown in FIG. 2, the firstbyte lane represented by data bit dq0 201 and corresponding dqs strobe202. The second byte lane is represented by dqs strobe 203 and data bitdq0 204. In general, the data and strobe signals connecting between aDDR memory and a DDR memory controller are organized such that each byteor eight bits of data has its own dqs strobe signal. Each of thesegroupings is referred to as a byte lane.

Looking at the data path starting with dq data bit 201 and dqs strobe202, these pass through programmable delay elements 205 and 206respectively before being stored in capture registers 207 and 208.Eventually these signals pass through a series of registers 209, 210,and 211 which are clocked by signals coming from tapped delay line 213.These registers form what is called a levelization FIFO and attempt toalign the data bits within a byte lane relative to other byte lanes.Tapped delay line 213 is driven by a PLL re-synchronization clockgenerator 214 which also drives the final stage registers 212 of thelevelization FIFO as well as being made available to the core circuitryof the controller. The PLL resynchronization clock generator 214 isphase and frequency synchronized with dqs. Notice that at this point,data stored in final stage registers 212 has not yet been captured bythe core clock of the memory controller. Also notice that the circuit ofFIG. 2 utilizes an individual delay element for each data bit such asdq0 201 and dq0 204.

When we examine fully-populated byte lanes, it should be noted that theadditional delay elements required to provide an individual programmabledelay on all incoming data bits can consume a large amount of siliconreal estate on the device containing a DDR memory controller circuit.Such a situation is shown in FIG. 3 where a single dqs strobe 301requires a single programmable delay 302, while the eight data bits 303of the byte lane each drive a programmable delay element 304.

FIG. 4 describes some of the timing relationships that occur for a priorart DDR memory controller which uses delay elements within the Phy forindividual read data bits.

FIG. 4a shows a simplified diagram where a single data bit isprogrammably delayed by element 401 in addition to the dqs strobe beingdelayed by element 402. Typically, data from input dq is captured onboth the rising and falling edges of dqs as shown in FIGS. 1 and 2,however for the sake of simplicity, the diagrams of FIGS. 3-12 only showthe schematic and timing for the dq bits captured on the rising edge ofdqs. By controlling both of these two delays, the output of captureregister 403 can be delayed by any amount within the range of the delayelements before it is passed into the core clock domain and clocked intoregister 404 by the Core_Clk signal 405. In FIG. 4b , the dqs_delayedsignal 406 is placed near the center of the valid window for dq 407 andafter being captured in register 403, data then enters the core domainat clock edge 408 is shown as shown. In this scenario the latency tomove the data into the core domain is relatively low simply because ofthe natural relationship between core clock and dqs. This relationshiphowever is extremely dependent upon the system topology and delays, andin fact could have almost any phase relationship.

A different phase relationship is possible as shown in FIG. 4c . Here, afirst edge 409 of Core_Clk happens to occur just before the leading edge410 of dqs_delayed. The result is that each data bit will not becaptured in the core clock domain until leading edge 411 of Core_Clk asshown, and thus will be delayed by amount of time 412 before beingtransferred into the core domain. Thus, while the ability to delay bothdq and dqs can accomplish synchronization with the core clock, it mayintroduce a significant amount of latency in the process.

A DDR memory controller circuit and method is therefore needed thatreliably captures and processes memory data during read cycles whilerequiring a small gate count resulting in implementations requiring asmall amount of silicon real estate. The controller should also offer ahigh yield for memory controller devices as well as a high yield formemory system implementations using those controller devices. Further,it is desirable to provide a DDR memory controller that is calibrated tocompensate for system level timing irregularities and for chip processparameter variations—that calibration occurring not only during power-upinitialization, but also dynamically during system operation to furthercompensate for power supply voltage variations over time as well assystem level timing variations as the system warms during operation.

Further it is useful to have a memory controller circuit that canperform a portion of calibration operations while allowing a signalgating window that is large, and then can perform further calibrationoperations and functional operation with an optimized signal gatingwindow.

Also, given the ever increasing clock rates that memories are capableof, it is useful to perform calibration and functional operation withsome number of related signals within a memory controller operating athalf the frequency of memory strobe signals such as DQS.

SUMMARY

In accordance with one embodiment, a computer-implemented method isprovided, comprising the act of: configuring code or hardware to causeat least part of the hardware to operate as a double data rate (DDR)memory controller and to: produce a capture clock to time a read datapath, where a timing of the capture clock is based on a first clocksignal of a first clock, delay the first clock signal to produce adelayed first clock signal, adjust the delay such that at least oneclock edge of the delayed first clock signal is placed nearer to atleast one clock edge of: at least one data strobe (DQS), or at least onesignal dependent on a DQS timing, and produce a modified timing of thecapture clock based on the delay of the first clock signal.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows a prior art DDR memory controller which utilizes anasynchronous FIFO with gated clock, all contained within the Phy portionof the controller circuit.

FIG. 2 shows a prior art DDR memory controller where delay elements areused on both dq and dqs signals and a form of FIFO is used for datalevelization, the FIFO being clocked by a clock that is PLL-synchronizedwith dqs, the entire circuit contained within the Phy portion of thememory controller.

FIG. 3 describes the read data path for a prior art DDR memorycontroller having delay elements on both dq and dqs inputs.

FIG. 4 shows the data capture and synchronization timing for the readdata path of a prior art DDR memory controller having delay elements onboth dq and dqs inputs.

FIG. 5 shows the read data path for a DDR memory controller according toan embodiment of the present invention where delay elements are used ondqs but not on dq inputs, and read data synchronization is performedwith the core clock by way of a core clock delay element.

FIG. 6 shows the data capture and synchronization timing for the readdata path of a DDR memory controller according to an embodiment of thepresent invention where delay elements are used on dqs but not on dqinputs, and read data synchronization is performed with the core clockby way of a core clock delay element.

FIG. 7 shows the read data path for a DDR memory controller according toone embodiment of the present invention including a CAS latencycompensation circuit which is clocked by the core clock.

FIG. 8 shows the glitch problem which can occur on the bidirectional dqssignal in DDR memory systems.

FIG. 9 shows a comparison of prior art memory controllers which utilizedelay elements on both dq and the dqs inputs when compared with thememory controller of one embodiment of the present invention, withemphasis on the number of total delay elements required for eachimplementation.

FIG. 10 shows a diagram for the read data path of a DDR memorycontroller according to one embodiment of the present invention withemphasis on the inputs and outputs for the Self Configuring Logicfunction which controls the programmable delay elements.

FIG. 11 describes the timing relationships involved in choosing thelarger passing window when the delay element producing Capture_Clk is tobe programmed according to one embodiment of the present invention.

FIG. 12 shows a timing diagram for the data eye indicating the commonwindow for valid data across a group of data bits such as a byte lane,given the skew that exists between all the data bits.

FIG. 13 shows a flow chart for the power-on initialization test andcalibration operation according to one embodiment of the presentinvention, the results of this operation including choosing programmabledelay values.

FIG. 14 shows the functionality of FIG. 10 with circuitry added toimplement a dynamically calibrated DDR controller function according toone embodiment of the invention, in particular to determine an optimumCapture_Clk delay.

FIG. 15 shows a timing diagram where Core_Clk and ip_dqs are delayed andsampled as part of implementing a dynamically calibrated DDR controllerfunction according to one embodiment of the invention.

FIG. 16 shows a flowchart describing the process of delaying andsampling both ip_dqs and Core_Clk, and for computing an optimumCapture_Clk delay.

FIG. 17 includes circuitry added for dynamic calibration, in particularfor a second phase according to the process of FIG. 18.

FIG. 18 shows a flowchart describing the process of iterativelycapturing read data from the DDR memory while sweeping different CASlatency compensation values to determine the settings for the DDR memorycontroller that provide the optimum CAS latency compensation.

FIGS. 19-22 show circuit details and timing relationships for providinga memory interface that includes two different windows for gating keytiming signals like DQS—a first that is large and allows for performinginitial calibration functions when the precise timing is not yet known,and a second for gating key timing signals more precisely as timingrelationships become more defined as the calibration process progresses.Also shown in FIGS. 19-22 are circuit details and timing relationshipsfor a memory interface that operates at substantially half a DQS clockrate, or a reduced clock rate, such that data can be captured accuratelyand calibration performed accurately even as primary clock rates formemories increase over successive technology generations.

FIGS. 23-26 depict additional details of the half frequency operation,pursuant to one embodiment of the invention.

DETAILED DESCRIPTION OF THE INVENTION

In contrast to prior art DDR memory controllers where calibrationfeatures for timing inconsistencies are implemented only in the Phyportion of the controller, the DDR memory controller of one embodimentof the present invention focuses on utilizing core domain clockingmechanisms, at times combined with circuitry in the Phy, to implement animproved solution for a timing-adaptive DDR memory controller.

In contrast with the prior art circuit of FIG. 4, FIG. 5 shows asimplified version of a DDR controller circuit according to anembodiment of the present invention. Here, the data inputs for a bytelane 501 are shown being captured in dq read data registers 502 withoutany additional delay elements added, these registers being clocked by adelayed version of dqs. The dqs clock signal 503 has dqs delay element504 added, typically delaying dqs by approximately 90 degrees relativeto the dqs signal driven by the DDR memory. The outputs of registers 502enter the core domain and are captured in first core domain registers505. Registers 505 are clocked by a delayed version of Core_Clk calledCapture_Clk 506. Capture_Clk is essentially the output of core clockdelay element 507 which produces a programmably delayed version ofCore_Clk 508. The outputs of first core domain registers 505 feed secondcore domain registers 509 which are clocked by Core_Clk. The amount ofdelay assigned to programmable delay element 507 is controlled by aself-configuring logic circuit (SCL) contained within the memorycontroller, this self-configuring logic circuit determining theappropriate delay for element 507 during a power-on initialization testand calibration operation.

FIG. 6 shows how the timing for the read data path can occur for the DDRmemory controller circuit of one embodiment of the present invention. Asimplified version of the read data path is shown in FIG. 6a where dqsis delayed by dqs delay element 601 which clocks dq into Phy datacapture register 602. The output of data capture register 602 then feedsthe first core domain register 603 which is clocked by Capture_Clk, theoutput of core clock delay element 604. The timing scenario shown inFIG. 6 occurs when the active edge of Core_Clk 605 (depicted in FIG.6(b)) occurs just after dq data 606 has been clocked into Phy datacapture register 602 by dqs_delayed 607. In this scenario, data can beimmediately clocked into first core domain register 603, and thus delayelement 604 may be programmably set to a delay of essentially zero,making the timing for Capture_Clk essentially the same as Core_Clk.

FIG. 6(c) a shows another timing scenario where the active edge ofCore_Clk 608 occurs just prior to dq data 609 being clocked into Phydata capture register 602 by dqs_delayed 610. As a result, core clockdelay element 604 will be programmed with delay 611 such that first coredomain register 603 is clocked on the active edge of Capture_Clk 612.Thus, regardless of the natural timing of Core_Clk relative to dqs,Capture_Clk will be positioned such that data will move from the Phydomain to the core domain in a predictable manner with minimal addedlatency due to random clock alignment.

FIG. 7 shows an embodiment for the present invention including a circuitthat compensates for CAS latency. According to Wikipedia: “CAS latency(CL) is the time (in number of clock cycles) that elapses between thememory controller telling the memory module to access a particularcolumn in the current row, and the data from that column being read fromthe module's output pins. Data is stored in individual memory cells,each uniquely identified by a memory bank, row, and column. To accessDRAM, controllers first select a memory bank, then a row (using the rowaddress strobe, RAS), then a column (using the CAS), and finally requestto read the data from the physical location of the memory cell. The CASlatency is the number of clock cycles that elapse from the time therequest for data is sent to the actual memory location until the data istransmitted from the module.” Thus, there is a timing unpredictabilityin any system implementation involving DDR memory between the readrequest from the controller to the memory and the resulting dataactually arriving back at the memory controller. The amount of thistiming unpredictability can be determined during the power-oninitialization test and calibration operation, and then compensated forby the circuit shown in FIG. 7 where the output of second core domainregister 701 feeds a partially populated array of registers 702, 703,and 704, which along with direct connection path 705 feed multiplexer706. These registers are all clocked by Core_Clk and thus createdifferent numbers of clock cycles of CAS latency compensation dependingupon which input is selected for multiplexer 706. During the power-oninitialization test and calibration operation, different inputs formultiplexer 706 will be selected at different times during the test inorder to determine which of the paths leading to multiplexer 706 isappropriate in order to properly compensate for the CAS delay in aparticular system installation.

In the earlier discussion with reference to FIG. 1, it was mentionedthat delay and gating element 109 was included in order to lower thepropensity for spurious glitches on dqs inadvertently clocking FIFO 101.The timing diagram of FIG. 8 shows this problem in more detail. Duringthe normal sequence of operation of a DDR memory, the dqs strobe isfirst driven by the memory controller during a write cycle and then,during a read cycle it is driven by the DDR memory. In between, thethere is a transitional time period 801 where the dqs connection mayfloat, that is not be driven by either the memory or the controller.During time periods 801, it is possible for glitches 802 to be inducedin dqs from a variety of sources including cross coupling from edges onother signals on boards or in the IC packages for the memory and/or thecontroller. In order to minimize the chance of any glitch on dqs causingdata corruption, the embodiment of the present invention as shown inFIGS. 5 through 7 allows capture clock 803 to be optimally positionedrelative to dqs_delayed 804 such that read data is always moved into thecore clock domain as early as possible.

FIG. 9 shows a comparison between an embodiment the present inventionand prior art memory controllers according to FIGS. 2 through 4, withemphasis on the amount of silicon real estate required based on thenumbers of delay elements introduced for an example implementationcontaining a total of 256 data bits. Notice in FIG. 9a that prior artmemory controllers that include delay elements on all dq data bits 901would require 256 delay elements 902 for dq inputs in addition to 16delay elements 903 for dqs inputs. In contrast to this, FIG. 9b shows animplementation according to one embodiment of the present inventionwhere only dqs input delay elements 904 are required and therefore thetotal number of delay elements in the Phy for an embodiment the presentinvention is 16 versus 272 for the prior art implementation of FIG. 9 a.

FIG. 10 shows a diagram of how the Self Configuring Logic (SCL) function1001 interfaces with other elements of the DDR memory controlleraccording to an embodiment of the present invention. In a firstembodiment of the present invention, the SCL 1001 receives the output1002 of the first core domain register (clocked by Capture_Clk) as wellas the output 1003 of the second core domain register (clocked byCore_Clk). In turn, the SCL provides output 1004 which controls thedelay of the delay element 1005 which creates Capture_Clk. The SCL alsodrives multiplexer 1006 which selects the different paths whichimplement the CAS latency compensation circuit as previously describedin FIG. 7 where multiplexer 706 performs this selection function.

In an alternate embodiment of the present invention, SCL 1001 alsoreceives data 1007 from input data register 1008, and in turn alsocontrols 1009 dqs delay element 1010, thereby enabling a much finerdegree of control for the dqs delay function than is normally utilizedin most memory controller designs, as well as allowing the dqs delay tobe initialized as part of the power on initialization test andcalibration operation.

FIG. 11 describes the concept behind the process for choosing the largerpassing window when positioning Capture_Clk. As described previously foran embodiment the present invention, the core clock signal is delayed inelement 1101 as shown in FIG. 11a to produce Capture_Clk. FIG. 11b showsa timing diagram where the RD_Data signal 1102 is to be captured infirst core domain register 1103. As shown in FIG. 11b , the position ofcore clock 1104 rarely falls in the center of the time that RD_Data 1102is valid, in this instance being position towards the beginning of thevalid time period 1105 for RD_Data. In this instance, two passingwindows 1106 and 1107 have been created, with 1106 being the smallerpassing window and 1107 being the larger passing window.

Therefore, in the scenario shown in FIG. 11b , some amount of programmeddelay 1108 would be programmed into delay element 1101 in order thatCapture_Clk 1109 may be positioned in the larger passing window 1107.

FIG. 12 shows a timing diagram for a group of data bits in a byte lanesuch as Rd_Data 1201 where the timing skew 1202 across the group of bitsis shown as indicated. The common time across all data bits in the groupwhere data is simultaneously valid is called the data eye 1203. Aftersubtracting setup time 1204 and hold time 1205 from data eye 1203, whatremains is the window within which Capture_Clk 1206 may be placed inorder to properly clock valid data on all bits of Rd_Data 1201 withinthe byte lane. Delay line increments 1207 represent the possible timingpositions that may be chosen for a programmable delay line to implementcore clock delay element 604 that produces Capture_Clk. For all systemsthere will be a minimum number of delay line increments 1207 for whichthe power on initialization test will determine that data is capturedsuccessfully, achieving that minimum number being necessary for themanufacturer of the system to feel confident that the timing margin isrobust enough for a production unit to be declared good. Thus, thisnumber of delay line increments that is seen as a minimum requirementfor a successful test is specified and stored in the system containingthe memory controller, and is utilized in determining if the power-oninitialization and calibration test is successful.

FIG. 13 shows a flow chart for the process implemented according to oneembodiment of the present invention for a power-on initialization testand calibration operation. Software or firmware controls this operationand typically runs on a processor located in the system containing theDDR memory and the controller functionality described herein. Thisprocessor may be located on the IC containing the memory controllerfunctionality, or may be located elsewhere within the system. In step1301, a minimum passing window requirement is specified in terms of aminimum number of delay increments for which data is successfullycaptured, as described in the diagram of FIG. 12. The minimum passingwindow requirement will be used to determine a pass or fail conditionduring the test, and also may be used in order to determine the numberof delay increments that must be tested and how many iterations of thetest loops (steps 1302 through 1307) must be performed. Steps 1302,1303, 1304, 1305, and 1306 together implement what in general is knownas nested “for” loops. Thus, for each latency delay value to be testedaccording to step 1302, each byte lane will be tested according to step1303. And, for each byte lane to be tested according to step 1303, eachdelay tap value within a chosen range of delay tap values will be testedaccording to step 1304. So, for each specific permutation of latencydelay, byte lane, and delay tap value, the BIST test (Built-In Self-Testfor the read data test) will be run according to step 1305, and a passor fail result will be recorded according to step 1306. Once alliterations of the nested “for” loops are completed as determined by step1307, the processor controlling the power-on initialization andcalibration test will then check (step 1308) to see if the minimumpassing window requirement has been met as specified in step 1301. Ifthe minimum has not been met, then the system will indicate a failure1311. If the requirement has been met, then according to step 1309 foreach byte lane the processor will choose the latency value that offersthe largest passing window, and then choose the delay tap value theplaces capture clock in the center of that window. Finally, values willbe programmed into control registers according to step 1310 such thatall delays within the controller system according to this invention areprogrammed with optimum settings.

Further, it is desirable to provide a DDR memory controller that iscalibrated to compensate for system level timing irregularities and forchip process parameter variations—that calibration occurring not onlyduring power-up initialization, but also dynamically during systemoperation to further compensate for power supply voltage variations overtime as well as system level timing variations as the system environmentvariables (such as temperature) change during operation. DSCL, a dynamicversion of the SCL or Self Configuring Logic functionality as describedherein, addresses the problem of VT (voltage and temperature) variationsduring normal operation of a chip that utilizes a DDR memory controlleras described herein to access a DRAM. Regular SCL as described earlieris typically run only on system power on. It can calibrate for thesystem level timing at the time it is run and can compensate for PVT(Process variations in addition to Voltage and Temperature) variationsthat occur from chip to chip, and do it in the context of the systemoperation.

Computer memory is vulnerable to temperature changes both in thecontroller and the corresponding memory modules. As any DDR memory chipor as the chip containing the DDR memory controller heat up, and supplyvoltage variations occur due to other external factors such as loadingexperienced by the power supply source, VT variations can cause systemlevel timing to change. These changes can affect the optimal programmingsettings as compared with those that were produced by operation of theSCL function when calibration was run at power on. Thus, DSCLfunctionality helps the chip to continuously compensate for VTvariations providing the best DRAM timing margin even as system timingchanges significantly over time. By performing the necessary calibrationin the shortest period of time, DSCL also ensures that the impact onsystem performance is minimal. DSCL divides the problem of calculatingthe Capture_Clk delay and the problem of CAS latency compensation intoseparate problems per FIGS. 16 and 18, and solves each of these problemsindependently. It also runs independently and parallely in each bytelane. Thus, the whole calibration process is greatly speeded up.Specifically, in one embodiment, if the user has an on-board CPU, thenon-dynamic SCL could be run within about 2 milliseconds assuming 4 bytelanes and 4 milliseconds for 8 byte lanes. In one embodiment of thedynamic SCL, regardless of 4 or 8 byte lanes, SCL would run within 1micro-second.

The operation of the DSCL functionality described herein utilizesportions of the existing SCL circuitry previously described and utilizesthat existing circuitry during both the calibration phase andoperational phase, however new circuitry is added for DSCL and thecalibration phase is broken into two sub-phases. One of these sub-phasescorresponds to the process described in FIG. 16, and the other sub-phasecorresponds to the process described in FIG. 18.

FIG. 14, when compared with FIG. 10, shows the circuit componentadditions which may be present in order to support the dynamicallycalibrated version of the DDR memory controller as described herein. Thepurpose of the additions to FIG. 10 as shown in FIG. 14 is to supportthe first phase of the SCL calibration whereby an optimum Capture_Clkdelay is determined according to the process of FIG. 16. The optimumCapture_Clk value is determined by the Self-configuring Logic 1001output 1004 to the Delay element 1005. Here, the delayed version of thedqs input signal produced by delay element 1010 and herein called ip_dqsis sampled in flip-flop 1413. Flip-flop 1413 is clocked by the output ofdelay element 1411 which delays Core_Clk. The output of flip-flop 1413is connected 1414 to the self configuring logic function 1001. Core_Clkis also delayed in delay element 1415 which in turn samples Core_Clk inflip-flop 1417. The output of flip-flop 1417 is connected 1418 to theself configuring logic function 1001. Delay elements 1411 and 1415 arecontrolled respectively by signals 1412 and 1416 from self configuringlogic function 1001. An output 1419 of SCL logic function 1001 controlsthe select lines of multiplexer 1006 which is the same multiplexer asshown earlier as multiplexer 706 in FIG. 7 and is used to selectcaptured read data which is delayed by different increments according towhich flip-flop delay chain path is most appropriate.

FIG. 15 graphically shows some of the timing delays that are manipulatedas part of the dynamic calibration sequence of the DDR memory controllerper one embodiment of the present invention and as described in FIG. 16.Here, Core_Clk 1501 is delayed by different values, here marked value“A” 1503 in FIG. 15. The ip_dqs signal 1502 is also delayed by differentvalues, here marked value “B” 1504.

FIG. 16 shows a flowchart for the dynamic calibration procedure in orderto determine an optimum delay for Core_Clk delay element 1005 in orderto produce an optimum timing for the Capture_Clk signal. In step 1601, asequence of read commands is issued so that the ip_dqs signal togglescontinuously. In step 1602, the Core_Clk signal is delayed and used tosample ip_dqs at different delay increments until a 1 to 0 transition isdetected on ip_dqs, whereby this value for the Core_Clk delay isrecorded as value “A”. In step 1603, the Core_Clk signal is delayed andused to sample Core_Clk at different delay increments until a 0 to 1transition is detected on Core_Clk, whereby this value for the Core_Clkdelay is recorded as value “B”. In step 1604, the optimum delay value“C” for delaying Core_Clk in order to produce an optimum Capture_Clksignal is computed according to the formula: if B−A>A then the resultingvalue C=(A+B)/2, otherwise C=A/2.

FIG. 17 shows the circuitry within the DSCL functionality that isutilized during the portion of the calibration sequence described in theprocess of FIG. 18. According to FIG. 11, read data has been captured inflip-flop 1103 by Capture_Clk to produce Rd_Data_Cap 1110. Rd_Data_Cap1110 is then captured in each of flip-flops 1701 on an edge of Core_Clkand are enabled to register Rd_Data_Cap by one of counters 1702 whichthemselves are also clocked by Core_Clk. Counters 1702 are enabled tostart counting by a Read Command 1703 issued by the DSCL functionality.The outputs of flip-flops 1701 each go to a data comparator 1704 wherethey are compared with a predefined data value 1705 which is stored inthe DDR memory controller in location 1706 and has also been previouslyplaced in the DDR memory itself as described in the process of FIG. 18.The outputs of the data comparators enter encoder 1707 whose output 1419controls multiplexer 1006 which chooses a flip-flop chain delay pathfrom those previously described in FIG. 7.

FIG. 18 shows a procedure for operating the DDR memory controller inorder to calibrate the controller during dynamic operation, and inparticular to determine the optimum overall CAS latency compensation.First, in step 1801 the Capture_Clk delay is set to the previouslydetermined optimum value according to the procedure described in theflowchart of FIG. 16. In step 1802 a known data pattern is read from aDDR memory connected to the DDR memory controller. This known datapattern originates in a stored location 1706 in the DDR controllerdevice and would typically have been previously saved or located in theDDR memory. If such a pattern is not available in the DDR memory, anappropriate pattern would be written to the DDR memory before this stepand subsequent steps are executed. If, in order to write such a knowndata pattern to the DDR memory, existing data at those memory locationsneeds to be preserved, the existing data may be read out and savedinside the memory controller or at another (unused) memory location, andthen may be restored after the DSCL dynamic calibration sequence perFIGS. 16 and 18 is run. In step 1803 read data is captured from the DDRmemory in an iterative manner while sweeping possible predetermined CASlatency compensation values from a minimum to a maximum value utilizingthe different delay paths that can be chosen with the circuitry shown inFIG. 17. In step 1804, when the read data matches at a particular CASlatency compensation, the parameters and settings that produced thatoptimum value of CAS latency compensation, i.e. the chosen delay paththrough the flip-flop chains feeding multiplexer 706 in combination withthe previously determined optimum Capture_Clk delay, are recorded as theoptimum parameters for the CAS latency compensation value and usedthereafter during normal operation until another dynamic calibrationsequence is performed.

Half-Frequency Operation and Dual-Mode DQS Gating Circuits and methodsare described for a DDR memory controller where two different DQS gatingmodes are utilized. These gating modes together ensure that the DQSsignal, driven by a DDR memory to the memory controller, is onlyavailable when read data is valid, thus eliminating capture ofundesirable data into the memory controller caused by glitches when DQSis floating. Two types of gating logic are used: Initial DQS gatinglogic, and Functional DQS gating logic. The Initial gating logic hasadditional margin to allow for the unknown round trip timing duringinitial bit levelling calibration. Eventually the memory controller willestablish precise timing in view of the actual round-trip delay. Roundtrip delay is the difference between the instant when a read command isissued by the memory controller and the instant when the correspondingdata from a DDR memory is received at the memory controller excludingthe known and fixed number of clock cycle delays involved in fetchingdata in the DDR protocol. Even though this round trip delay has not beencharacterized when initial bit-levelling calibration is performed, it isuseful to perform bit-levelling early in the overall calibration processas this makes subsequent phase and latency calibration for data capturemore precise and consistent across all data bits. During bit-levellingcalibration an alternating pattern of 1s and 0s is read from the memoryand the memory controller is able to perform bit-levelling regardless ofthe round-trip delay due to the predictable nature of the pattern andthe manner in which bit-leveling calibration operates. This does,however, require a wider window for DQS gating and hence the Initialgating mode as described herein is used. Please see co-pending U.S. Ser.No. 13/797,200 for details on calibration for bit-levelling. DQSfunctional gating is optimized to gate DQS precisely as Capture_Clkdelay and CAS latency compensation calibration is performed. This gatingfunctionality is especially useful when data capture into a core clockdomain is performed at half the DQS frequency in view of rising clockrates for DDR memories.

With newer DDR technologies, memory speeds are becoming faster andfaster. This means that the period of the clocks are becoming smallerand smaller. This is problematic for successful data capture because therelated timing windows also become smaller. By operating with some ofthe clocks involved in data capture at the half frequency, as well asother associated logic, the size of these timing windows can beincreased. Whereas while operating at full frequency, SCL couldtheoretically choose a position for Capture_Clk in such a way that inputDQS gating is not necessary, when running at half frequency such anoption no longer exists. This is because the input DQS needs to bedivided to half its frequency using a toggling flip-flop to produce asignal shown as dl_half_rate_dqs 2103 in FIG. 21. If dl_half_rate_dqswere to toggle because of a spurious noise pulse on input DQS 1903 inFIG. 19, or when DQS is toggling at other times not corresponding to avalid input being driven from the DRAM 1904, then it could have anopposite polarity from what is required to latch the input data from theDRAM correctly.

Especially when some of the capture-related clocks and logic areoperated at half frequency, it can become problematic during a first runof bit-levelling calibration when the gating for input DQS 1902 may notyet be perfect. In such a condition, it may be unclear how to bestopen/close DQS gating, since write side bit-levelling may need the gateto be open either perfectly or for more time. An initial gating strategyis therefore used for the first bit-levelling calibration because it ismore lenient in that it will leave the gate open for a larger amount oftime before closing it. This does not cause a problem for thebit-leveling function to work properly since it does not depend ondl_half_rate_dqs to perform its function. This capability and extramargin is not needed after SCL calibration is performed, as describedearlier in this specification with respect to Self-Configuring Logic1001, because the gating can then be programmed more precisely withinthe functional gating mode using the information obtained by SCL.

This capability to use two gating modes of operation is also useful foran implementation even where the clocks are operated at full frequency,in view of the smaller available timing margins as memory access clockspeeds continue to rise from year to year.

The waveform of FIG. 19 shows a hypothetical example of the goal of DQSGating by only allowing the DQS pulses that correspond to the issuedread command to be operated on by the memory controller. As shown inFIG. 20, there are two types of gating logic, the Initial gating logic2002, and the Functional gating logic 2003. The difference between thetwo is how precisely they work. The Initial gating logic 2002 hasadditional margin to allow for the unknown input DQS round trip timingduring initial bit-levelling calibration. The Functional gating logic2003 gates DQS precisely based on the round trip timing informationdiscovered and refined during SCL calibration. Regardless of whichgating logic is active, either 2002 or 2003, the resulting output is agated ip_dqs called ip_dqs (post gate) 2005. There is also a disablecontrol 2004 that can be used which forgoes gating but it is not advisedto turn it on with half-frequency mode since glitches can invert thephase of the divided DQS.

FIG. 20 shows a high-level block diagram representation for the logicused for both Initial DQS gating 2002 and for Functional DQS gating2003. The Initial gating mode is only used for the first time thatbit-levelling calibration is run. At this initial point in thecalibration process, SCL calibration has not yet been run. Therefore,the Functional gate timing would be imprecise if used at this stage ofthe calibration process. After the first time bit levelling is run usingInitial DQS gating, Functional gating mode is used during SCLcalibration and for functional operation after determination of precisetiming values for Capture_clk 2105 and CAS latency calibration.Thereafter, whenever bit levelling or dynamic SCL calibration are runfrom time to time during functional system operation, the Functionalgating timing is used.

Functional gating timing has not been optimized prior to the first runof SCL calibration for optimizing Capture_clk 2105 timing. During thefirst run of SCL calibration, the gate opening timing is not precise, soit is possible that for half-frequency operation—for applications wherehalf-frequency functionality according to the present invention isused—the divided input DQS, called dl_half_rate_dqs 2103, has theopposite phase from what is required. This situation is automaticallydetected and corrected by SCL calibration as described below withrespect to SCL Clock Domain Crossing. After SCL calibration hascompleted, the just discovered Capture_Clk and CAS latency settings areused to close the gate precisely, for functional operation and for anyfurther calibration operations.

SCL Clock Domain Crossing and Half-Frequency Capture Logic

One exemplary circuit used to implement the read capture logic is shownin FIG. 21 for applications where half-frequency functionality accordingto the present invention is used. As described earlier in thisspecification, capture_clk 2105 is the variable delay clock which SCLwill tune so that there is optimal setup and hold margins for clockingdata from the input DDR3/DDR4 strobe domain to the memory controller'score clock domain, where it is captured by core_clk 2104.

During SCL operation, the memory controller will continuously look forthe location of the second falling edge of ip_dqs 2102. This is the edgein which valid data on ip_dq 2101 will be available. The data will crossclock domains from this edge to the falling edge of dl_half_rate_dqs2103 which happens on the same edge of ip_dqs that triggereddl_half_rate_dqs to go low. This is done to reduce latency on the readpath but it must be noted that to check timing based on this, amulti-cycle path of zero is used to time the path during Static TimingAnalysis. SCL will find the center between the rising edge of core_clkand the falling edge of the next dl_half_rate_dqs strobe, shown bypoints A 2201 and B 2202 in the FIG. 22. Whichever point gives thelargest setup and hold margins—point B in the example below—will be setas the active edge location for capture_clk.

Phase Fixing

As described above, valid read data is available after the secondfalling edge of ip_dqs or the falling edge of the divided DQS,dl_half_rate_dqs. It is possible that dl_half_rate_dqs could start orbecome out of phase. If out of phase, the data read back will not becorrect. SCL calibration has the ability to detect this situation. OnceSCL finishes calibration, it will check to see if it failed or not. Ifit passed, the phase is correct and normal functionality will follow. Ifit failed, SCL will run CAS latency calibration again after flipping thepolarity of dl_half_rate_dqs placing it back into phase. The setting forCapture_Clk will also be recalculated by moving point A in FIG. 22either forward or backward by 1 cycle of ip_dqs based on whether A islesser or greater than one cycle of ip_dqs.

Logic for Initial Gating During Initial Bit Levelling Calibration

In the Initial gating mode, the gate is extended 8 full rate cyclesbeyond the falling edge of rd_data_en_scl 2001 to ensure maximum roundtrip delay in receiving valid DQS pulses is accounted for. This isexemplary, and extension by other numbers of full rate cycles ispossible.

FIG. 23, shows an example timing diagram of the fundamental signals ininitial ABC gating routine to create the final gating signal. Thesignals shown in FIG. 23 are defined as follows:

-   Full Rate Clock 2301: One of two clock domains in the memory    controller with the same frequency as ip_dqs and is used sparingly    as some portions of the memory controller must be in the full rate    domain.-   Read Data Enable SCL 2001: Read enable signal from the memory    controller which is used for calibration purposes and to control the    DQS gate signal.-   Read Data Enable SCL Delayed 2303: This is the read data enable SCL    signal but delayed by two full rate cycles.-   Read Data Enable Count 2304: A counter which is used to extend the    final DQS gate signal by eight full rate cycles.-   Read Data Enable SCL Extended 2305: A one bit signal derived from    the read data enable count to extend the final DQS gate by eight    cycles.-   DQS Gate Final 2306: This signal will gate DQS but it has no concept    of round trip time and therefore opens earlier and closes later    giving more margins. (NOTE: this signal is the same one used for    functional gating, but the logic to have the gate open/close is    different since the round trip time is known)-   DQS 2307: The incoming DQS from the memory.

Note that in FIG. 23 the round trip delay here looks relatively small asthe drawing has been simplified. Round trip delay is the time it takesfor the read data and strobe to be received at the memory controllerafter the memory has received the read address and command issued by thememory controller. The read data enable SCL delayed signal will openbefore the DQS strobe is received by the memory controller as it is muchmore lenient.

Before SCL calibration has been run, the memory controller does not knowanything about the round trip time and therefore the gate will notopen/close perfectly. This is why Initial gating mode is used since itis much more lenient on when it opens and closes the gate, thus notinterfering with bit levelling calibration. Again, Initial gating modein half frequency mode is only used during the initial run of bitlevelling calibration for both the read and write side. When the memorycontroller is going start reading data for calibration, it will generatea read data enable signal which takes in account the read latency of thememory. When this read data enable signal is used for gating, it isdelayed further by two cycles. This is exemplary and could be delayedmore or less. The delayed version of the read data enable signal willopen the gate albeit a bit earlier than the time when the DQS from thememory reaches the memory controller. At the falling edge of the delayedread data enable signal, the memory controller will extend the gatingsignal by 8 full rate cycles and then will close it. The position atwhich it closes will be after the DQS has arrived at the memorycontroller from the memory.

Logic for Functional Gating (Functional Gating Logic) The logic forgenerating the functional gating signal is more intricate. It isnecessary to being gating shortly before the rising edge of the firstDQS pulse during the preamble and to stop gating shortly after the lastfalling edge during the postamble as shown in FIG. 25.

How each of the gating logic functions fits in the overall memoryinterface according to the invention is shown in the schematic blockdiagram per FIG. 24 in conjunction with the timing diagram of FIG. 25.

Gate Opening Timing for Functional Gating

Per FIG. 25, in order to begin gating just before the first pulse ofDQS, it must be determined when the first pulse actually occurs withrespect to something that is known. Note that there is also an analog ordigital DLL that is used to delay the input DQS by ¼ cycle for centeringit with respect to DQ. The waveforms of FIG. 25 show the timing of thegating signal with respect to ip_dqs prior 2102 to being delayed by theDLL (pre DLL) as well as after being delayed 2401 by the DLL (post DLL).In FIG. 25 with respect to half-frequency operation, dl_half_rate_dqs2103 is a divided version of ip_dqs (post DLL) 2401 which toggles onevery falling edge of ip_dqs (post DLL). When SCL calibration runs, itdetermines the phase difference between the rising edge of core_clk 2104and the falling edge of dl_half_rate_dqs 2103 which corresponds to thesecond falling edge of ip_dqs (post DLL) 2401 and stores this value as avariable called cycle_cnt (this is the same as the SCL measurement pointA mentioned previously with respect to FIG. 22). Therefore, theinvention uses cycle_cnt as a reference to determine when ip_dqs willpulse with respect to core_clk so gating can being beforehand.

First cycle_cnt_clk 2402 is created by delaying core_clock by the valuecycle_cnt. This new clock (cycle_cnt_clk) has each positive edge alignedto each second falling edge of ip_dqs (post DLL). Another clock,cycle_cnt_modified_clk 2403 is generated ¼ Full rate clock cycle sooneror one and ¾ Full rate clock cycle later than cycle_cnt_clk (dependingon whether cycle_cnt is greater than ¼ Full rate clock cycle or lessthan ¼ cycle respectively).

It can be seen that each positive edge of cycle_cnt_modified_clk 2403 isaligned to each second falling edge of ip_dqs (pre DLL) 2102 and istherefore centered in the middle of ip_dqs preamble time—as shown by thedotted line 2501 in FIG. 25.

Next, the read enable signal from the controller is registered into thisnew cycle_cnt_modified_clk domain using capture_clk and cycle_cnt_clk asstaging clocks. Capture_Clk is guaranteed by SCL calibration to bepositioned so that maximum setup and hold margins are obtained whentransitioning between the core_clk and cycle_cnt_clk domains. Timingfrom cycle_cnt_clk to cycle_cnt_modified_clk is met by design. This readenable signal, once latched in the cycle_cnt_modified_clk domain, isused to signal the start of DQS gating. The clock cycle latency of theread enable signal is also adjusted based on SCL calculated CAS latencyas described previously. Also, the enable signal is shortened by 1 clockcycle compared to the length of the read burst so that it does notaffect the gate closing timing.

Gate Closing

Per FIG. 26, the DQS gate is closed directly by the last falling edge ofthe final DQS pulse. This is done by latching the third staged read dataenable signal (in cycle_cnt_clk domain) into the dl_half_rate_dqsdomain.

Thus, the foregoing description of preferred embodiments of the presentinvention has been provided for the purposes of illustration anddescription. It is not intended to be exhaustive or to limit theinvention to the precise forms disclosed. Many modifications andvariations will be apparent to one of ordinary skill in the relevantarts. For example, unless otherwise specified, steps performed in theembodiments of the invention disclosed can be performed in alternateorders, certain steps can be omitted, and additional steps can be added.The embodiments were chosen and described in order to best explain theprinciples of the invention and its practical application, therebyenabling others skilled in the art to understand the invention forvarious embodiments and with various modifications that are suited tothe particular use contemplated. It is intended that the scope of theinvention be defined by the claims and their equivalents.

1. A computer-implemented method, comprising an act of: configuring hardware to cause at least a part of the hardware to operate as a double data rate (DDR) memory controller, and to: produce a capture clock to time a read data path, where a timing of the capture clock is based on a first clock signal of a first clock; delay the first clock signal to produce a delayed first clock signal; adjust the delay such that at least one clock edge of the delayed first clock signal is placed nearer to at least one clock edge of: at least one data strobe (DQS); or at least one signal dependent on a DQS timing; and produce a modified timing of the capture clock based on the delay of the first clock signal.
 2. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the first clock signal is a core clock signal or a signal derived from at least the core clock signal.
 3. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to issue a sequence of read commands so that at least one of: the at least one DQS toggles repeatedly; or the at least one signal dependent on the DQS timing toggles repeatedly.
 4. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the adjusting the delay produces a plurality of the clock edges of the delayed first clock signal that are a function of the least one clock edge.
 5. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the at least one clock edge includes the at least one clock edge of the at least one signal dependent on the DQS timing, and the at least one clock edge is a delayed version of another at least one DQS.
 6. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to adjust the timing of the capture clock by monitoring the DQS timing or a signal dependent on the DQS timing.
 7. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to produce the capture clock such that the capture clock runs at a same clock frequency as a memory clock of a memory.
 8. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to produce the capture clock such that the capture clock at a clock frequency that is the same as, a multiple of, or a sub-multiple of a frequency of read data in the read data path.
 9. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to use a calibration sequence to place the capture clock in a more optimum sampling position in a read data eye.
 10. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the capture clock is adjusted to place capture of read data closer to a middle of a data eye.
 11. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that read data is captured directly in one or more registers.
 12. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that read data is directly captured from memory.
 13. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the capture clock is adjusted to increase a reliability of a capture of read data from a memory.
 14. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that a read timing training calibration sequence is performed to increase a reliability of a capture of read data from a memory.
 15. The method of claim 14, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that at least one delay element is adjusted during the read timing training calibration sequence.
 16. The method of claim 15, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the adjustment of the at least one delay element causes an adjustment of a phase of the capture clock.
 17. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the capture clock is produced by a capture clock generation circuit.
 18. The method of claim 17, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the capture clock generation circuit adjusts a timing of the capture clock to match a phase of a memory clock of a memory.
 19. The method of claim 1, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the modified timing of the capture clock accommodates at least one of a variation of voltage or a variation of temperature.
 20. The method of claim 19, and comprising an additional act of further configuring the hardware to cause the at least part of the hardware to operate such that the accommodation is performed by at least one of a capture clock generation circuit or a circuit driving a capture clock generation circuit. 